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june 2007 rev 4 1/22 22 tsh350 550mhz low noise current feedback amplifier features bandwidth: 550mhz in unity gain quiescent current: 4.1ma slew rate: 940v/ s input noise: 1.5nv/ hz distortion: sfdr=-66dbc (10mhz, 1v pp ) 2.8v pp minimum output swing on 100 load for a 5v supply tested on 5v power supply applications communication & video test equipment medical instrumentation adc drivers description the tsh350 is a current feedback operational amplifier using a very high-speed complementary technology to provide a bandwidth up to 410mhz while drawing only 4.1ma of quiescent current. with a slew rate of 940v/s and an output stage optimized for driving a standard 100 load, this circuit is highly suitable for applications where speed and power-saving are the main requirements. the tsh350 is a single operator available in the tiny sot23-5 and so-8 plastic packages, saving board space as well as providing excellent thermal and dynamic performance. pin connections (top view) 1 2 3 5 4 vcc - vcc + + - non-inv. in. inv. in. sot23-5 output 1 2 3 5 4 vcc - vcc + + - non-inv. in. inv. in. sot23-5 output inv. in. non-inv. in. vcc - vcc + 1 2 3 5 4 8 7 6 nc nc output + _ nc so-8 inv. in. non-inv. in. vcc - vcc + 1 2 3 5 4 8 7 6 nc nc output + _ nc so-8 sot23-5 so-8 www.st.com
absolute maximum ratings tsh350 2/22 1 absolute maximum ratings table 1. absolute maximum ratings (amr) symbol parameter value unit v cc supply voltage (1) 1. all voltage values are measur ed with respect to the ground pin. 6v v id differential input voltage (2) 2. differential voltage is the non-inverting input termi nal with respect to the inverting input terminal. +/-0.5 v v in input voltage range (3) 3. the magnitude of input and output voltage must never exceed v cc +0.3v. +/-2.5 v t stg storage temperature -65 to +150 c t j maximum junction temperature 150 c r thja thermal resistance junction to ambient sot23-5 so-8 250 150 c/w r thjc thermal resistance junction to case sot23-5 so-8 80 28 c/w p max maximum power dissipation (4) (@t amb =25c) for t j =150c sot23-5 so-8 4. short-circuits can cause excessive heating. destructive dissipation can result from sh ort-circuits on all amplifiers. 500 830 mw esd hbm: human body model (5) pins 1, 4, 5, 6, 7 and 8 pins 2 and 3 5. human body model: a 100pf capacitor is charged to the specified voltage, then discharged through a 1.5k resistor between two pins of the device. this is done for all couples of connected pin combinations while the other pins are floating. 2 0.5 kv mm: machine model (6) pins 1, 4, 5, 6, 7 and 8 pins 2 and 3 6. machine model: a 200pf capacitor is charged to the specified voltage, then discharged directly between two pins of the device with no external series resistor (int ernal resistor < 5 ). this is done for all couples of connected pin combinations whil e the other pins are floating. 200 60 v cdm: charged device model (7) pins 1, 4, 5, 6, 7 and 8 pins 2 and 3 7. charged device model: all pins and the package are charged together to the specified voltage and then discharged directly to the ground through only one pin. th is is done for all pins. 1.5 1.5 kv latch-up immunity 200 ma
tsh350 absolute maximum ratings 3/22 table 2. operating conditions symbol parameter value unit v cc supply voltage (1) 4.5 to 5.5 v v icm common mode input voltage -v cc +1.5v to +v cc -1.5v v t oper operating free air temperature range -40 to + 85 c 1. tested in full production at 5v (2.5v) supply voltage.
electrical characteristics tsh350 4/22 2 electrical characteristics table 3. electrical characteristics for v cc = 2.5v, t amb = 25c (unless otherwise specified) symbol parameter test conditions min. typ. max. unit dc performance v io input offset voltage offset voltage between both inputs t amb 0.8 4 mv t min < t amb < t max 1 v io v io drift vs. temperature t min < t amb < t max 0.9 v/c i ib+ non inverting input bias current dc current necessary to bias the input + t amb 12 35 a t min < t amb < t max 13 i ib- inverting input bias current dc current necessary to bias the input - t amb 120 a t min < t amb < t max 2.5 cmr common mode rejection ratio 20 log ( v ic / v io ) v ic = 1v 56 60 db t min < t amb < t max 58 svr supply voltage rejection ratio 20 log ( v cc / v io ) v cc =+3.5v to +5v 68 81 db t min < t amb < t max 78 psr power supply rejection ratio 20 log ( v cc / v out) a v = +1, v cc =100mv at 1khz 51 db t min < t amb < t max 48 i cc positive supply current dc consumption with no input signal no load 4.1 4.9 ma dynamic performance and output characteristics r ol transimpedance output voltage/input current gain in open loop of a cfa. for a vfa, the analog of this feature is the open loop gain (a vd ) v out = 1v, r l = 100 170 270 k t min < t amb < t max 250 k bw -3db bandwidth frequency where the gain is 3db below the dc gain a v note: gain bandwidth product criterion is not applicable for current-feedback-amplifiers small signal v out =20mv pp a v = +1, r l = 100 a v = +2, r l = 100 a v = +10, r l = 100 a v = -2, r l = 100 250 550 390 125 370 mhz gain flatness @ 0.1db band of frequency where the gain variation does not exceed 0.1db small signal v out =100mv p a v = +1, r l = 100 65 sr slew rate maximum output speed of sweep in large signal v out = 2v pp , a v = +2, r l = 100 940 v/ s v oh high level output voltage r l = 100 1.44 1.56 v t min < t amb < t max 1.49
tsh350 electrical characteristics 5/22 v ol low level output voltage r l = 100 -1.53 -1.44 v t min < t amb < t max -1.49 i out i sink short-circuit output current coming in the op- amp (see figure 9 ) output to gnd 135 205 ma t min < t amb < t max 195 i source output current coming out from the op-amp (see figure 10 ) output to gnd -140 -210 t min < t amb < t max -185 noise and distortion en equivalent input noise voltage see section 5: noise measurements f = 100khz 1.5 nv/ hz in equivalent input noise current (+) see section 5: noise measurements f = 100khz 20 pa/ hz equivalent input noise current (-) see section 5: noise measurements f = 100khz 13 pa/ hz sfdr spurious free dynamic range the highest harmonic of the output spectrum when injecting a filtered sine wave a v = +1, v out = 1v pp f = 10mhz f = 20mhz f = 50mhz f = 100mhz -66 -57 -46 -42 dbc table 3. electrical characteristics for v cc = 2.5v, t amb = 25c (unless otherwise specified) symbol parameter test conditions min. typ. max. unit table 4. closed-loop gain and feedback components v cc (v) gain r fb ( ) -3db bw (mhz) 0.1db bw (mhz) 2.5 +10 300 125 22 -10 300 120 20 +2 300 390 110 -2 300 370 70 +1 820 550 65 -1 300 350 120
electrical characteristics tsh350 6/22 figure 1. frequency response, positive gain figure 2. frequency response, negative gain 1m 10m 100m 1g -10 -8 -6 -4 -2 0 2 4 6 8 10 12 14 16 18 20 22 24 gain=+1 gain=+2 gain=+4 small signal vcc=5v load=100 gain=+10 gain (db) frequency (hz) 1m 10m 100m 1g -10 -8 -6 -4 -2 0 2 4 6 8 10 12 14 16 18 20 22 24 gain=-1 gain=-2 gain=-4 small signal vcc=5v load=100 gain=-10 gain (db) frequency (hz) figure 3. compensation, gain=+4 f igure 4. compensation, gain=+2 1m 10m 100m 11,6 11,7 11,8 11,9 12,0 12,1 + - 100r 300r 4pf vin vout gain=+4, vcc=5v, small signal + - 100r 300r 4pf vin vout gain=+4, vcc=5v, small signal gain flatness (db) frequency (hz) 1m 10m 100m 1g 5,6 5,7 5,8 5,9 6,0 6,1 6,2 gain=+2, vcc=5v, small signal + - 100r 300r 2pf vin vout 8k2 gain=+2, vcc=5v, small signal + - 100r 300r 2pf vin vout 8k2 gain flatness (db) frequency (hz) figure 5. frequency response vs. capacitor load figure 6. step response vs. capacitor load 1m 10m 100m 1g -10 -8 -6 -4 -2 0 2 4 6 8 10 + - 300r 300r vin vout gain=+2, vcc=5v, small signal r-iso 1k c-load + - 300r 300r vin vout gain=+2, vcc=5v, small signal r-iso 1k c-load c-load=10pf r-iso=39ohms c-load=22pf r-iso=27ohms c-load=1pf r-iso=22ohms gain (db) frequency (hz) 0,0s 2,0ns 4,0ns 6,0ns 8,0ns 10,0ns 12,0ns 14,0ns 16,0ns 18,0ns 20,0ns -1 0 1 2 3 + - 300r 300r vin vout gain=+2, vcc=5v, small signal r-iso 1k c-load + - 300r 300r vin vout gain=+2, vcc=5v, small signal r-iso 1k c-load c-load=10pf r-iso=39ohms c-load=22pf r-iso=27ohms c-load=1pf r-iso=22ohms output step (volt) time (ns)
tsh350 electrical characteristics 7/22 figure 7. slew rate figure 8. output amplitude vs. load -2ns -1ns 0s 1ns 2ns 3ns 0,0 0,5 1,0 1,5 2,0 gain=+2 vcc=5v load=100 output response (v) time (ns) 10 100 1k 10k 100k 2,0 2,5 3,0 3,5 4,0 gain=+2 vcc=5v load=100 max. output amplitude (vp-p) load (ohms) figure 9. i sink figure 10. i source -2,0 -1,5 -1,0 -0,5 0,0 0 50 100 150 200 250 300 + _ r g +2.5v -2.5v v ol without load v isink amplifier in open loop without load -1v + _ r g +2.5v -2.5v v ol without load v isink amplifier in open loop without load -1v isink (ma) v (v) 0,0 0,5 1,0 1,5 2,0 -300 -250 -200 -150 -100 -50 0 + _ r g +2.5v -2.5v v oh without load v isource amplifier in open loop without load +1v + _ r g +2.5v -2.5v v oh without load v isource amplifier in open loop without load +1v isource (ma) v (v) figure 11. input current noise vs. frequency figure 12. input voltage noise vs. frequency 1k 10k 100k 1m 10m 10 20 30 40 50 60 70 neg. current noise pos. current noise i n (pa/sqrt(hz)) frequency (hz) 1k 10k 100k 1m 10m 1.0 1.5 2.0 2.5 3.0 3.5 4.0 e n (nv/sqrt(hz)) frequency (hz)
electrical characteristics tsh350 8/22 figure 13. quiescent current vs. v cc figure 14. distortion vs. output amplitude 1,25 1,50 1,75 2,00 2,25 2,50 -5 -4 -3 -2 -1 0 1 2 3 4 5 gain=+2 vcc=5v input to ground, no load icc (ma) icc(+) icc(-) +/-vcc (v) 01234 -80 -75 -70 -65 -60 -55 -50 -45 -40 -35 -30 -25 -20 -15 -10 -5 0 hd3 hd2 gain=+2 vcc=5v f=30mhz load=100 hd2 & hd3 (dbc) output amplitude (vp-p) figure 15. distortion vs. output amplitude figure 16. noise figure 01234 -100 -95 -90 -85 -80 -75 -70 -65 -60 -55 -50 -45 -40 -35 -30 -25 -20 hd3 hd2 gain=+2 vcc=5v f=10mhz load=100 hd2 & hd3 (dbc) output amplitude (vp-p) 1 10 100 1k 10k 100k 0 5 10 15 20 25 30 35 40 gain=? vcc=5v nf (db) rsource (ohms) figure 17. distortion vs. output amplitude fi gure 18. output amplitude vs. frequency 01234 -100 -95 -90 -85 -80 -75 -70 -65 -60 -55 -50 -45 -40 -35 -30 -25 -20 hd3 hd2 gain=+2 vcc=5v f=20mhz load=100 hd2 & hd3 (dbc) output amplitude (vp-p) 1m 10m 100m 1g 0 1 2 3 4 5 gain=+2 vcc=5v load=100 vout max. (vp-p) frequency (hz)
tsh350 electrical characteristics 9/22 figure 19. reverse isolation vs. frequency figure 20. svr vs. temperature 1m 10m 100m 1g -100 -80 -60 -40 -20 0 small signal vcc=5v load=100 isolation (db) frequency (hz) -40 -20 0 20 40 60 80 100 120 50 55 60 65 70 75 80 85 90 gain=+1 vcc=5v load=100 svr (db) temperature (c) figure 21. bandwidth vs. temperature figure 22. r ol vs. temperature -40 -20 0 20 40 60 80 100 120 200 250 300 350 400 450 500 550 gain=+1 vcc=5v load=100 bw (mhz) temperature (c) -40 -20 0 20 40 60 80 100 120 200 220 240 260 280 300 320 340 open loop vcc=5v r ol (m ) temperature (c) figure 23. cmr vs. temperature figure 24. i bias vs. temperature -40-20 0 20406080100120 50 52 54 56 58 60 62 64 66 68 70 gain=+1 vcc=5v load=100 cmr (db) temperature (c) -40 -20 0 20 40 60 80 100 120 -4 -2 0 2 4 6 8 10 12 14 gain=+1 vcc=5v load=100 i bias ( a) ib(+) ib(-) temperature (c)
electrical characteristics tsh350 10/22 figure 25. v io vs. temperature figure 26. i cc vs. temperature -40 -20 0 20 40 60 80 100 120 0 200 400 600 800 1000 open loop vcc=5v load=100 temperature (c) v io (micro v) -40 -20 0 20 40 60 80 100 120 -10 -8 -6 -4 -2 0 2 4 6 gain=+1 vcc=5v no load in+/in- to gnd icc(+) icc(-) temperature (c) i cc (ma) figure 27. v oh and v ol vs. temperature figure 28. i out vs. temperature -40-20 0 20406080 -5 -4 -3 -2 -1 0 1 2 gain=+1 vcc=5v load=100 v ol v oh v oh & ol (v) temperature (c) -40-20 0 20406080100120 -400 -300 -200 -100 0 100 200 300 output: short-circuit gain=+1 vcc=5v iout (ma) isource isink temperature (c)
tsh350 evaluation boards 11/22 3 evaluation boards an evaluation board kit optimized for high-speed operational amplifiers is available (order code: kithseval/stdl). as well as a cd-rom containing datasheets , articles, application notes and a user manual, the kit includes the following evaluation boards: sot23_single_hf board board for the evaluation of a single high-speed op-amp in sot23-5 package. so8_single_hf board for the evaluation of a single high-speed op-amp in so-8 package. so8_dual_hf board for the evaluation of a dual high-speed op-amp in so-8 package. so8_s_multi board for the evaluation of a single high-speed op-amp in so-8 package in inverting and non-inverting configuration, dual and single supply. so14_triple board for the evaluation of a triple high-speed op-amp in so-14 package with video application considerations. board material: 2 layers fr4 ( r=4.6) epoxy 1.6mm copper thickness: 35m figure 29. evaluation kit for high-speed op-amps
power supply considerations tsh350 12/22 4 power supply considerations correct power supply bypassing is very important for optimizing performance in high- frequency ranges. bypass capacitors should be pl aced as close as possible to the ic pins to improve high-frequency bypassing. a capacitor greater than 1 f is necessary to minimize the distortion. for better quality bypassing, a capacitor of 10nf can be added which should also be placed as close as possible to the ic pins. bypass capacitors must be incorporated for both the negative and the positive supply. note: on the so8_single_hf board, these capacitors are c6, c7, c8, c9. figure 30. circuit for power supply bypassing single power supply in the event that a single supply system is us ed, biasing is necessary to obtain a positive output dynamic range between 0v and +v cc supply rails. considering the values of v oh and v ol , the amplifier will provide an output swing from +0.9v to +4.1v on a 100 load. the amplifier must be biased wit h a mid-supply (nominally +v cc /2), in order to maintain the dc component of the signal at this value. several options are possible to provide this bias supply, such as a virtual ground using an operational amplifier or a two-resistance divider (which is the cheapest solution). a high resistance value is required to limit the current consumption. on the other hand, the current must be high enough to bias the non-inverting input of the amplifier. if we consider this bias current (35 a maximum) as 1% of the current through the resistance divider, to keep a stable mid-supply, two resistances of 750 can be used. the input provides a high-pass filter with a break frequency below 10hz which is necessary to remove the original 0 volt dc component of the input signal, and to fix it at +v cc /2. figure 31 illustrates a 5v single power supply configuration for the so8_s_multi evaluation board (see evaluation boards on page 11). + -v cc +v cc 10f + 10nf 10f + 10nf - + -v cc +v cc 10f + 10nf 10f + 10nf -
tsh350 power supply considerations 13/22 a capacitor c g is added in the gain network to ensure a unity gain in low frequency to keep the right dc component at the output. c g contributes to a high-pass filter with r fb //r g and its value is calculated with a consideration of the cut off frequency of this low-pass filter. figure 31. circuit for +5v single supply (using evaluation board so8_s_multi) + _ r2 750 r g in +5v 100 out r fb 10f + 1f 100f r1 750 +5v 10nf r in 1k c g + + _ r2 750 r g in +5v 100 out r fb 10f + 1f 100f r1 750 +5v 10nf r in 1k c g +
noise measurements tsh350 14/22 5 noise measurements the noise model is shown in figure 32 : en is the input voltage noise of the amplifier inn is the negative input cu rrent noise of the amplifier inp is the positive input cu rrent noise of the amplifier figure 32. noise model the thermal noise of a resistance r is where f is the specified bandwidth. on a 1hz bandwidth the thermal noise is reduced to: where k is the boltzmann's constant, equal to 1,374.10-23j/k. t is the temperature (k). the output noise eno is calculated using the superposition theorem. however, eno is not the simple sum of all noise sources, but rather the square root of the sum of the square of each noise source, as shown in equation 1 : equation 1 + _ r3 r1 output r2 in- in+ hp3577 input noise: 8nv/ hz n1 n2 n3 en + _ r3 r1 output r2 in- in+ hp3577 input noise: 8nv/ hz n1 n2 n3 en 4ktr f 4ktr eno v1 2 v2 2 v3 2 v4 2 v5 2 v6 2 +++++ =
tsh350 noise measurements 15/22 equation 2 the input noise of the instrumentation must be extracted from the measured noise value. the real output noise value of the driver is: equation 3 the input noise is called equivalent input noise because it is not directly measured but is evaluated from the measurement of the output divided by the closed loop gain (eno/g). after simplification of the fourth and the fifth term of equation 2 we obtain: equation 4 measurement of the input voltage noise en if we assume a short-circuit on the non-inverting input (r3=0), from equation 4 we can derive: equation 5 in order to easily extract the va lue of en, the resistance r2 w ill be chosen to be as low as possible. in the other hand, the gain must be large enough: r3=0, gain: g=100 measurement of the negativ e input current noise inn to measure the negative input current noise inn, we set r3=0 and use equation 5 . this time, the gain must be lower in order to decrease the thermal noise contribution: r3=0, gain: g=10 measurement of the positi ve input current noise inp to extract inp from equation 3 , a resistance r3 is connected to the non-inverting input. the value of r3 must be chosen in order to keep its thermal noise contribution as low as possible against the inp contribution: r3=100w, gain: g=10 eno 2 en 2 g 2 inn 2 r2 2 inp 2 + + r3 2 g 2 r2 r1 ------- - 2 4ktr1 4ktr2 1 r2 r1 ------- - + 2 4ktr3 ++ + = eno measured () 2 instrumentation () 2 ? = eno 2 en 2 g 2 inn 2 r2 2 inp 2 + + r3 2 g 2 g4ktr21 r2 r1 ------- - + 2 4ktr3 + + = eno en 2 g 2 inn 2 r2 2 g4ktr2 + + =
intermodulation distortion product tsh350 16/22 6 intermodulation distortion product the non-ideal output of the amplifier can be described by the following series: where the input is v in =asin t, c 0 is the dc component, c 1 (v in ) is the fundamental and c n is the amplitude of the harmonics of the output signal v out . a one-frequency (one-tone) input signal contributes to harmonic distortion. a two-tone input signal contributes to harmonic distortion and to the intermodulation product. the study of the intermodulation and distortion for a two-tone input signal is the first step in characterizing the driving capab ility of multi-tone input signals. in this case: then: from this expression, we can extract the distortion terms, and the intermodulation terms from a single sine wave: second order intermodulation terms im2 by the frequencies ( 1 - 2 ) and ( 1 + 2 ) with an amplitude of c2a 2 third order intermodulation terms im3 by the frequencies (2 1 - 2 ), (2 1 + 2 ), ( ? 1 +2 2 ) and ( 1 + 2 2 ) with an amplitude of (3/4)c3a 3 the intermodulation product of the driver is measured by using the driver as a mixer in a summing amplifier co nfiguration (see figure 33 ). in this way, the non-linearity problem of an external mixing device is avoided. figure 33. inverting summing amplifier (using evaluation board so8_s_multi) v out c 0 c 1 v in c 2 v 2 in c + n v n in ++ + = v in a 1 t sin a 2 t sin + = v out c 0 c 1 a 1 t sin a 2 t sin + () c 2 a 1 t sin a 2 t sin + () 2 c n a 1 t sin a 2 t sin + () n ++ + = + _ r r fb 100 v out r 2 v in2 v in1 r 1 + _ r r fb 100 v out r 2 v in2 v in1 r 1
tsh350 inverting amplifier biasing 17/22 7 inverting amplifier biasing a resistance is necessary to achieve good input biasing, such as resistance r shown in figure 34 . the magnitude of this resistance is calculated by assuming the negative and positive input bias current. the aim is to compensate for the offset bias current, which could affect the input offset voltage and the output dc component. assuming i ib- , i ib+ , r in , r fb and a zero volt output, the resistance r is: figure 34. compensation of the input bias current r r in r fb r in r + fb ------------------------ = r load output r fb r in i ib- i ib+ v cc+ v cc- + _ r load output r fb r in i ib- i ib+ v cc+ v cc- + _
active filtering tsh350 18/22 8 active filtering figure 35. low-pass active filtering, sallen-key from the resistors r fb and r g we can directly calculate the gain of the filter in a classic non- inverting amplificat ion configuration: we assume the following expressi on as the response of the system: the cut-off frequency is not gain-dependent and so becomes: the damping factor is calculated by the following expression: the higher the gain, the more sensitive the damping factor is. when the gain is higher than 1, it is preferable to use some very stable resistor and capacitor values. in the case of r1=r2=r: due to a limited selection of va lues of capacitors in comparison with resistors, we can set c1=c2=c, so that: + _ r g in r fb 910 100 out r 1 r 2 c 2 c 1 + _ r g in r fb 910 100 out r 1 r 2 c 2 c 1 a v g1 r fb r g -------- + == t j vout j vin j ---------------- - g 12 j c ----- j () 2 c 2 ----------- - ++ ---------------------------------------- - == c 1 r1r2c1c2 ------------------------------------ - = 1 2 -- - c c 1 r 1 c 1 r 2 c 2 r 1 c 1 r 1 g ? ++ () = 2c 2 c 1 r fb r g -------- ? 2c 1 c 2 -------------------------------- - = 2r 2 r 1 r fb r g -------- ? 2r 1 r 2 -------------------------------- - =
tsh350 package information 19/22 9 package information figure 36. sot23-5 package mechanical data ref. dimensions millimeters mils min. typ. max. min. typ. max. a 0.90 1.45 35.4 57.1 a1 0.00 0.15 0.00 5.9 a2 0.90 1.30 35.4 51.2 b 0.35 0.50 13.7 19.7 c 0.09 0.20 3.5 7.8 d 2.80 3.00 110.2 118.1 e 2.60 3.00 102.3 118.1 e1 1.50 1.75 59.0 68.8 e 0.95 37.4 e1 1.9 74.8 l 0.35 0.55 13.7 21.6
package information tsh350 20/22 figure 37. so-8 package mechanical data ref. dimensions millimeters inches min. typ. max. min. typ. max. a1.750.069 a1 0.10 0.25 0.004 0.010 a2 1.25 0.049 b 0.28 0.48 0.011 0.019 c 0.17 0.23 0.007 0.010 d 4.80 4.90 5.00 0.189 0.193 0.197 h 5.80 6.00 6.20 0.228 0.236 0.244 e1 3.80 3.90 4.00 0.150 0.154 0.157 e 1.27 0.050 h 0.25 0.50 0.010 0.020 l 0.40 1.27 0.016 0.050 k1818 ccc 0.10 0.004
tsh350 ordering information 21/22 10 ordering information 11 revision history table 5. order codes part number temperature range package packing marking TSH350Ilt -40c to +85c sot23-5 tape & reel k305 TSH350Id so-8 tube TSH350I TSH350Idt so-8 tape & reel TSH350I date revision changes 1-oct-2004 1 first release corresponding to preliminary data version of datasheet. 10-dec-2004 2 release of mature product datasheet. 21-jun-2005 3 in ta b l e 1 on page 2, r thjc thermal resistance junction to ambient replaced by thermal resistance junction to case. 8-jun-2007 4 format update.
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